Wireless communication method and apparatus for performing post-detection constellation correction

ABSTRACT

A method and apparatus for correcting the phase and gain of data associated with a constellation pattern of a plurality of received individual symbols. Each symbol is divided into real and imaginary symbol components. The signs of the real and imaginary symbol components of each symbol are determined and used as a basis for determining whether the symbol is associated with a first or third quadrant of the constellation pattern or a second or fourth quadrant of the constellation pattern. The absolute values of the real and imaginary symbol components are determined and used to create a first sum and a second sum. A phase adjustment value θ and a gain adjustment value G are derived from the first and second sums, and are used to create a complex number. Each of the received individual symbols is multiplied by the created complex number to provide corrected constellation pattern data.

CROSS REFERENCE TO RELATED APPLICATION

This application claims priority from U.S. Provisional PatentApplication Ser. No. 60/519,102, filed Nov. 12, 2003, which isincorporated by reference as if fully set forth herein.

FIELD OF INVENTION

The invention relates to a wireless communication receiver. Moreparticularly, the present invention relates to the reception of wirelesssignals in the presence of imperfect channel estimation.

BACKGROUND

When a transmission is made in a multipath environment, the propagatingchannel introduces distortions in the transmitted signal which degradethe signal quality at the receiver. In many wireless communicationssystems, knowledge of the channel state is required to properlydemodulate the transmission. Thus, a channel estimate is performed atthe receiver and is subsequently used to demodulate data.

Quadrature amplitude modulation (QAM) is a method of combining twoamplitude-modulated (AM) signals into a single channel, thereby doublingthe effective bandwidth. QAM is used with pulse amplitude modulation(PAM) in digital systems, especially in wireless applications. In a QAMsignal, there are two carriers, each having the same frequency butdiffering in phase by ninety degrees, (i.e., one quarter of a cycle,from which the term quadrature arises). One signal is called the real orin-phase (I) signal and the other is called the imaginary or quadrature(Q) signal. Mathematically, one of the signals can be represented by asine wave, and the other by a cosine wave. The two modulated carriersare combined at the source for transmission. At the destination, thecarriers are separated, the data is extracted from each, and then thedata is combined into the original modulating information.

In digital applications, the modulating signal is generally quantized inboth its in-phase and ninety degree components. The set of possiblecombinations of amplitudes, as shown on an x-y plot, is a pattern ofdots known as a QAM constellation. This constellation, and therefore thenumber of bits which can be transmitted at once, can be increased forhigher bit rates and faster throughput, or decreased for more reliabletransmission with fewer bit errors. The number of “dots” in theconstellation is given as a number before the QAM, and is often aninteger power of two, i.e., from 2¹ (2QAM) to 2¹² (4096QAM).

In many wireless systems, such as frequency division duplex (FDD), timedivision duplex (TDD), and IEEE 802.11 systems, the channel estimate isperformed based on a known transmission, i.e., a pilot signal. However,the channel state changes over a period of time and therefore thechannel estimate may no longer be an accurate estimate of the channelduring much of the transmission. The effect of the channel drift, inpart, can be seen in the constellation diagram of a packet of receivedsymbols as distinctly non-Gaussian noise or distortion about theconstellation points.

One method to compensate for channel drift is to perform channelestimates at a higher rate. When the pilot signal is time multiplexedwith the data, this may be difficult. When the pilot signal iscontinuously transmitted, channel estimates can be performed at anarbitrary rate, but may pose an unacceptable computational burden orprocessing delay.

Adaptive receivers, such as normalized least mean squared (NLMS)equalizers, also suffer degradation that can be seen in theconstellation diagram even when a continuous pilot signal is present. Inthis case, it is not the lack of current channel estimation that causesthe distortion, but rather it is due to the receiver remaining in atracking state and thus never converges. The effect is equivalent to theabove description of receivers that have channel estimates that becomeincreasingly unreliable after they are created, i.e., the adaptivereceiver has an implied channel estimate that is always delayed andtherefore is not completely reflective of the current channelconditions.

SUMMARY

The present invention is related to a wireless communication method andapparatus for correcting the phase and gain of data associated with aconstellation pattern of a plurality of received individual symbols. Theapparatus may be a receiver, a wireless transmit/receive unit (WTRU)and/or an integrated circuit (IC).

In accordance with the present invention, each individual symbol isdivided into real and imaginary symbol components. The signs of the realand imaginary symbol components of each symbol are determined and usedas a basis for determining whether the symbol is associated with a firstor third quadrant, (i.e., a first quadrant union), of the constellationpattern or a second or fourth quadrant, (i.e., a second quadrant union),of the constellation pattern. The first and second quadrant unionspartition the constellation space. The absolute values of the real andimaginary symbol components are determined and used to create a firstsum and a second sum. A sum ratio m is determined by dividing the firstsum by the second sum. A predetermined function is performed on sumratio m to determine a phase adjustment value θ. A gain adjustment valueG is determined by adding the first and second sums together. A complexnumber is created based on the phase adjustment value θ and the gainadjustment value G. Each of the received individual symbols ismultiplied by the created complex number to provide correctedconstellation pattern data.

BRIEF DESCRIPTION OF THE DRAWINGS

A more detailed understanding of the invention may be had from thefollowing description, given by way of example and to be understood inconjunction with the accompanying drawings wherein:

FIG. 1 shows a 16QAM constellation diagram of a received packet ofsymbols for a conventional post-detection channel without constellationcorrection;

FIG. 2 shows a 16QAM constellation diagram of a received packet ofsymbols for a conventional IEEE 802.11 post-detection channel using a“stale channel estimate”;

FIG. 3 shows a 16QAM constellation representation of a post-detectionchannel after constellation correction has been applied in accordancewith the present invention;

FIG. 4 is a block diagram of a receiver for partitioning incoming data,estimating gain and phase corrections, and applying the gain and phasecorrections to the symbols in the constellation in accordance with apreferred embodiment of the present invention; and

FIGS. 5A and 5B, taken together, are a flow chart of a process includingmethod steps implemented by the receiver of FIG. 4.

DETAILED DESCRIPTION OF THE PREFERRED EMBODIMENT(S)

The preferred embodiments will be described with reference to thedrawing figures where like numerals represent like elements throughout.

Hereafter, the terminology “WTRU” includes but is not limited to a userequipment (UE), a mobile station, a fixed or mobile subscriber unit, apager, or any other type of device capable of operating in a wirelessenvironment.

The present invention is applicable to any type of wirelesscommunication systems such as universal mobile telecommunications systemTDD (UMTS-TDD) and FDD, time division synchronous code division multipleaccess (TD-SCDMA), code division multiple access 2000 (CDMA 2000), andCDMA in general or any other type of wireless communication system. Withrespect to CDMA 2000, the present invention may be implemented in EV-DO(i.e. data only) and EV-DV (i.e. data and voice).

The features of the present invention may be incorporated into an IC orbe configured in a circuit comprising a multitude of interconnectingcomponents.

The present invention is generally applicable to a typical receiver witha channel estimator, but may also be applicable to an adaptive receiver.Once a channel estimate is calculated, that estimate is used for sometime period afterwards under the assumption that the estimate remainssufficiently accurate. However, for a third generation partnershipproject (3GPP) VA120 channel model, (i.e., a channel model correspondingto a mobile station traveling at 120 kph), when the channel variesrapidly compared to the channel estimate update rate due to the rapidlymoving mobile station, the assumed channel estimate may becomeinaccurate because the constellation pattern of the detected receiversymbols may exhibit phase errors, gain errors and non-Gaussiancharacteristics.

FIG. 1 illustrates a post-detection 16QAM constellation for a VA120model channel without constellation correction. The constellation shownin FIG. 1 has non-Gaussian distortion and a decreased signal-to-noiseratio (SNR).

FIG. 2 shows the effect of using a “stale channel estimate” in a highvelocity mobile IEEE 802.11(a) system, which is also clearly visible asa non-Gaussian noise distribution upon the 16QAM. A “stale channelestimate” refers to the situation when the channel varies rapidlycompared to the channel estimate update rate. In other words, a channelthat has changed substantially since the last time it was estimated is a“stale channel estimate.”

The noise distributions tend to have ridges in the complex plane thatcan be well described by a simple function of time, t, with t=0 at thetime the channel estimate was made in accordance with the presentinvention. For example, the ridge locations in polar coordinates for thepost multi-user detector (MUD) symbols in a 3GPP VA120 channel model arewell described by the parametric Equations (1) and (2) as follows:r(t)=r ₀ +r ₁ t  Equation (1)θ(t)=θ₀+θ₁ t  Equation (2)where t is the time since the channel estimate, r(t), is the radialdistance from the origin, and θ(t) is the angle distance. The parametersr₀ and θ₀ correspond to an amplitude and phase, and the parameters r₁and θ₁ correspond to an amplitude drift and phase drift. In general,additional terms corresponding to greater powers of t may be included.

FIG. 3 shows the resulting constellation after application of a processimplemented in accordance with the present invention after theapplication of the constellation correction process reflected inEquations (1) and (2). The characteristics of the constellationillustrated in FIG. 3 are superior to those in FIGS. 1 and 2 because theconstellation points are closer to their reference constellation pointsand become more Gaussian in their distribution. Thus, the probability ofbit error is reduced and the SNR is significantly increased.

Upon making a hard decision for each symbol, a gain and phase errorassociated with each symbol is formed. The present invention estimatesthe parameters r₀, r₁, . . . , r_(n) and θ₀, θ₁, . . . , θ_(n), based onthe estimated errors for each sysmbol, (e.g., by variations of linearregression or other methods used for curve fitting) and the correctionis applied to the entire constellation based on the estimates.

The above-mentioned process can be iterated to increase theeffectiveness if desired because as the constellation becomes morecorrected, fewer symbols may cause hard decision errors.

It is not necessary to use all of the detected symbols, or to give themequal weight, when estimating the parameters r₀, r₁, . . . , r_(n) andθ₀, θ₁, . . . , θ_(n). Since the estimated symbols nearest the time ofthe channel estimate are better, these symbols may be considered withhigher weight as they are most likely to result in correct harddecisions. A subset of the symbols that correspond to a ‘fresh’ channelestimate may be used while ignoring the other symbols.

The same idea is easily extended to cases where frequency divisionmultiplexing (FDM) is employed, (e.g., OFDM, DMT, COFDM, MC-CDMA, or thelike). In such cases, the channel estimates may not only be restrictedto certain time intervals but also to certain frequency intervals. Forexample, in an IEEE 802.11(a) system, pilot signals are provided atselected times and frequencies.

The method of constellation correction according to Equations (1) and(2) is applicable to the type of noise distribution associated with FDMsystems. A more general form of Equations (1) and (2) that incorporatehigher orders terms in both time (t) and frequency (f) may be writtenas:

$\begin{matrix}\begin{matrix}{{r\left( {t,f} \right)} = {r_{0,0} + {r_{1,0}t} + r_{0,{1f}} + {r_{1,1}t\; f} + {r_{2,0}t^{2}} + \ldots}} \\{= {\sum\limits_{i,j}{r_{i,j}t^{i}f^{j}}}}\end{matrix} & {{Equation}\mspace{14mu}(3)} \\\begin{matrix}{{\theta\left( {t,f} \right)} = {\theta_{0,0} + {\theta_{1,0}t} + \theta_{0,{1f}} + {\theta_{1,1}{tf}} + {\theta_{2,0}t^{2}} + \ldots}} \\{= {\sum\limits_{i,j}{\theta_{i,j}t^{i}f^{j}}}}\end{matrix} & {{Equation}\mspace{14mu}(4)}\end{matrix}$

In a special case where only the 0^(th) order corrections are required,(i.e., the bulk phase/gain terms that don't depend on t),simplifications may be made to reduce complexity of the presentinvention. The present invention is particularly useful in adaptivereceivers and applies to a large class of constellations withoutrequiring hard decisions to be made. The correction of gain requiresonly averaging the magnitude of the real and imaginary components of theconstellation points to find and correct the gain error. To find andcorrect the phase, additional categorization of real and imaginarycomponents, (based on their signs, i.e., the quadrant of the symbol), isrequired, but adds negligibly to the complexity. The bulk phase error ofthe constellation can be computed from a ratio of a partition into twosuch categories. The phase error is well approximated by a simplefunction of the ratio.

FIG. 4 is a block diagram of a receiver 400 for partitioning incomingdata, estimating gain and phase corrections, and applying the gain andphase corrections to the symbols in the constellation in accordance witha preferred embodiment of the present invention.

The receiver 400 includes a symbol component divider 405, a realcomponent sign detector 410A, an imaginary component sign detector 410B,a quadrant union detector 415, absolute value units 420A, 420B, logicalrouter 425, summers 430A and 430B, ratio calculation unit 435, adder440, ratio function unit 445, complex number generator 460, andmultiplier 470.

FIGS. 5A and 5B, taken together, are a flow chart of a process 500including method steps, implemented by the receiver 400 of FIG. 4, forcorrecting a post-detection constellation.

Referring to FIGS. 4 and 5A, the receiver 400 receives constellationdata including a plurality of individual symbols at input 402 (step505). Each symbol is a complex number having a real and imaginary symbolcomponent. In step 510, each individual symbol is divided, (i.e.,split), by the symbol component divider 405 into real and imaginarysymbol components. In step 515, the real component sign detector 410Aand the imaginary component sign detector 410B determine the sign,(i.e., polarity), of each of the real and imaginary symbol components,respectfully, outputted by the symbol component divider 405. In step520, the quadrant union detector 415 determines, based on the outputs ofthe real component sign detector 410A and the imaginary component signdetector 410B, whether the individual symbol is associated with a firstor third quadrant, (i.e., a first quadrant union), of a constellation,or a second or fourth quadrant, (i.e., a second quadrant union), of theconstellation.

Referring to FIG. 4, the real and imaginary symbol components outputtedby the symbol component divider 405 are also respectively fed to theabsolute value units 420A, 420B, which output the absolute values, 422Aand 422B, of the real and imaginary symbol components, respectively. Theabsolute values, 422A and 422B are fed to respective inputs of thelogical router 425. Based on output 418 of the quadrant union detector415, which indicates which quadrant union each individual symbolcomponent is associated with, each of the absolute values 422A and 422Bare fed to one of the summers 430A and 430B.

Referring to FIGS. 4 and 5A, in step 525, one of the summers, 430A,creates a first sum, sum A, of the absolute values of the real symbolcomponents associated with the second quadrant union and the imaginarysymbol components associated with the first quadrant union.

In step 530, the other one of the summers, 430B, creates a second sum,sum B, of the absolute values of the real symbol components associatedwith the first quadrant union and the imaginary symbol componentsassociated with the second quadrant union.

A description of how the summers 430A and 430B create sum A and sum Bwill now be described. As previously mentioned, data received at theinput 402 of the receiver 400 includes a group of symbols, (i.e.,complex numbers). The symbols are “split” into real and imaginary symbolcomponents by the symbol component detector 405 and the absolute valuesare taken by the absolute value units 420A and 420B, resulting in twogroups of numbers: 1) group A—an imaginary symbol component group ofnumbers; and 2) group B—a real symbol component group of numbers. On aper symbol basis, the logical router 425 swaps some of the numbers inthe “real symbol component” group with the corresponding numbers in the“imaginary symbol component” group. Swapping occurs if the correspondingsymbol is in the first or third quadrant, as determined by the quadrantunion detector 415, whereby its output 418 controls the logical router425.

For example, if the first symbol received by the receiver 400 via theinput 402 is in the first or third quadrant, the first number in thereal symbol component group A is swapped with the first number in theimaginary symbol component group B. If the second symbol received by thereceiver 400 via the input 402 is in the second or fourth quadrant, anumber exchange between the second numbers in groups A and B does notoccur, and so on. This process is applied to each received symbol.

All of the numbers in group A are summed up in the summer 430A and allthe numbers in group B are summed up in the summer 430B. The inputprovided by the logical router 425 into each of the summers 430A and430B is a group of numbers, whereas the output of each of the summers430A and 430B is a single number.

Referring now to FIGS. 4 and 5B, in step 535, the ratio calculation unit435 receives sum A and sum B from the outputs of the summers 430A and430B, and divides sum A by sum B to obtain a resulting sum ratio m whichthe ratio calculation unit 435 outputs to the ratio function unit 445.In step 540, the ratio function unit 445 performs a simple predeterminedfunction on m, (e.g., (m−1)/2), to estimate a phase adjustment value θ450, which is the phase of the constellation in radians. In step 545,the adder 440 adds together the outputs of the summers 430A and 430 B toestimate a gain adjustment value G 455, which is the estimated gain ofthe constellation.

In step 550, the phase adjustment value θ 450 and the gain adjustmentvalue G 455 are input to the complex number generator 460 which performsa complex number function, to create, for example, a complex number 465with an amplitude equal to the inverse of the gain adjustment value G455, and a phase equal to the phase adjustment value θ 450, (i.e.,1/G×e^(jθ)). In step 555, data associated with the constellation iscorrected by the multiplier 470 multiplying the data symbols received atinput 402 by the created complex number 465 to output the resultingcorrected data 475. Finally, in step 560, if further correction isdesired, the corrected data 475 is used as the received constellation ofstep 505 which is fed to the input 402, and steps 510–555 are repeated.

While the present invention has been described in terms of the preferredembodiment, other variations which are within the scope of the inventionas outlined in the claims below will be apparent to those skilled in theart.

1. A method for correcting the phase and gain of data associated with aconstellation pattern of a plurality of received individual symbols, theconstellation pattern having a first quadrant union including a firstquadrant and a third quadrant, and a second quadrant union including asecond quadrant and a fourth quadrant, the method comprising: (a)dividing each individual symbol into real and imaginary symbolcomponents; (b) determining the signs of the real and imaginary symbolcomponents; (c) determining whether the individual symbol is associatedwith the first quadrant union or the second quadrant union based on thesigns determined in step (b); (d) determining the absolute values of thereal and imaginary symbol components; (e) creating a first sum of theabsolute values of the real symbol components determined in step (c) asbeing associated with the second quadrant union and the absolute valuesof the imaginary symbol components determined in step (c) as beingassociated with the first quadrant union; (f) creating a second sum ofthe absolute values of the real symbol components determined in step (c)as being associated with the first quadrant union and the absolutevalues of the imaginary symbol components determined in step (c) asbeing associated with the second quadrant union; (g) determining a sumratio m by dividing the first sum by the second sum; (h) performing apredetermined function on the sum ratio m to determine a phaseadjustment value θ; (i) determining a gain adjustment value G by addingthe first and second sums together; (j) creating a complex number basedon the phase adjustment value θ and the gain adjustment value G; and (k)multiplying each of the received individual symbols by the createdcomplex number to provide corrected constellation pattern data.
 2. Themethod of claim 1 wherein the predetermined function performed on thesum ratio m is (m−1)/2.
 3. The method of claim 1 wherein the createdcomplex number has a amplitude equal to the inverse of the gainadjustment value G, and a phase equal to the phase adjustment value θ.4. The method of claim 1 wherein the method is implemented by afrequency division multiplexing (FDM) system, and the constellationpattern data is corrected as a function of time and frequency.
 5. Areceiver for correcting the phase and gain of data associated with aconstellation pattern of a plurality of individual symbols received byan input to the receiver, the constellation pattern having a firstquadrant union including a first quadrant and a third quadrant, and asecond quadrant union including a second quadrant and a fourth quadrant,the receiver comprising: (a) a symbol component divider for dividingeach individual symbol into real and imaginary symbol components, thesymbol divider being configured to output the real symbol components viaa first output and the imaginary symbol components via a second output;(b) a real component sign detector in communication with the firstoutput of the symbol component divider for receiving the real symbolcomponents and determining the signs of the real symbol components; (c)an imaginary component sign detector in communication with the secondoutput of the symbol component divider for receiving the imaginarysymbol components and determining the signs of the imaginary symbolcomponents; (d) a quadrant union detector in communication with the realcomponent sign detector and the imaginary component sign detector forreceiving an indication of the signs of the real and imaginary symbolcomponents of the individual symbol, the quadrant union detector beingconfigured to identify whether the individual symbol is associated withthe first quadrant union or the second quadrant union based on thereceived indication; (e) a first absolute value unit in communicationwith the first output of the symbol component divider for outputting theabsolute values of the real symbol components; (f) a second absolutevalue unit in communication with the second output of the symbolcomponent divider for outputting the absolute values of the imaginarysymbol components; (g) a first summer for creating a first sum of theabsolute values of the real symbol components identified by the quadrantunion detector as being associated with the second quadrant union andthe absolute values of the imaginary symbol components identified by thequadrant union detector as being associated with the first quadrantunion; (h) a second summer for creating a second sum of the absolutevalues of the real symbol components identified by the quadrant uniondetector as being associated with the first quadrant union and theabsolute values of the imaginary symbol components identified by thequadrant union detector as being associated with the second quadrantunion; (i) a ratio calculation unit in communication with the first andsecond summers for determining a sum ratio m by dividing the first sumby the second sum; (j) a ratio function unit in communication with theratio calculation unit for performing a predetermined function on thesum ratio m to determine a phase adjustment value θ; (k) an adder incommunication with the first and second summers for determining a gainadjustment value G by adding the first and second sums together; (l) acomplex number generator in communication with the adder and the ratiofunction unit for creating a complex number based on the phaseadjustment value θ and the gain adjustment value G; and (m) a multiplierin communication with the input to the receiver and the complex numbergenerator for multiplying each of the received individual symbols by thecreated complex number, wherein the multiplier outputs correctedconstellation pattern data.
 6. The receiver of claim 5 wherein thepredetermined function performed on the sum ratio m is (m−1)/2.
 7. Thereceiver of claim 5 wherein the created complex number has a amplitudeequal to the inverse of the gain adjustment value G, and a phase equalto the phase adjustment value θ.
 8. The receiver of claim 5 wherein thereceiver operates in conjunction with a frequency division multiplexing(FDM) system, and the constellation pattern data is corrected as afunction of time and frequency.
 9. The receiver of claim 5 furthercomprising: (n) a logical router in communication with the first andsecond absolute value units, the first and second summers, and thequadrant union detector, wherein the logical router is configured toroute absolute values of the real symbol components to the first summerbased on whether the quadrant union detector identifies the real symbolcomponents as being associated with the first quadrant union or thesecond quadrant union.
 10. The receiver of claim 5 further comprising:(n) a logical router in communication with the first and second absolutevalue units, the first and second summers, and the quadrant uniondetector, wherein the logical router is configured to route absolutevalues of the imaginary symbol components to the first summer based onwhether the quadrant union detector identifies the imaginary symbolcomponents as being associated with the first quadrant union or thesecond quadrant union.
 11. The receiver of claim 5 further comprising:(n) a logical router in communication with the first and second absolutevalue units, the first and second summers, and the quadrant uniondetector, wherein the logical router is configured to route absolutevalues of the real symbol components to the second summer based onwhether the quadrant union detector identifies the real symbolcomponents as being associated with the first quadrant union or thesecond quadrant union.
 12. The receiver of claim 5 further comprising:(n) a logical router in communication with the first and second absolutevalue units, the first and second summers, and the quadrant uniondetector, wherein the logical router is configured to route absolutevalues of the imaginary symbol components to the second summer based onwhether the quadrant union detector identifies the imaginary symbolcomponents as being associated with the first quadrant union or thesecond quadrant union.
 13. A wireless transmit/receive unit (WTRU) forcorrecting the phase and gain of data associated with a constellationpattern of a plurality of individual symbols received by an input to theWTRU, the constellation pattern having a first quadrant union includinga first quadrant and a third quadrant, and a second quadrant unionincluding a second quadrant and a fourth quadrant, the WTRU comprising:(a) a symbol component divider for dividing each individual symbol intoreal and imaginary symbol components, the symbol divider beingconfigured to output the real symbol components via a first output andthe imaginary symbol components via a second output; (b) a realcomponent sign detector in communication with the first output of thesymbol component divider for receiving the real symbol components anddetermining the signs of the real symbol components; (c) an imaginarycomponent sign detector in communication with the second output of thesymbol component divider for receiving the imaginary symbol componentsand determining the signs of the imaginary symbol components; (d) aquadrant union detector in communication with the real component signdetector and the imaginary component sign detector for receiving anindication of the signs of the real and imaginary symbol components, thequadrant union detector being configured to identify whether theindividual symbol is associated with the first quadrant union or thesecond quadrant union based on the received indication; (e) a firstabsolute value unit in communication with the first output of the symbolcomponent divider for outputting the absolute values of the real symbolcomponents; (f) a second absolute value unit in communication with thesecond output of the symbol component divider for outputting theabsolute values of the imaginary symbol components; (g) a first summerfor creating a first sum of the absolute values of the real symbolcomponents identified by the quadrant union detector as being associatedwith the second quadrant union and the absolute values of the imaginarysymbol components identified by the quadrant union detector as beingassociated with the first quadrant union; (h) a second summer forcreating a second sum of the absolute values of the real symbolcomponents identified by the quadrant union detector as being associatedwith the first quadrant union and the absolute values of the imaginarysymbol components identified by the quadrant union detector as beingassociated with the second quadrant union; (i) a ratio calculation unitin communication with the first and second summers for determining a sumratio m by dividing the first sum by the second sum; (j) a ratiofunction unit in communication with the ratio calculation unit forperforming a predetermined function on the sum ratio m to determine aphase adjustment value θ; (k) an adder in communication with the firstand second summers for determining a gain adjustment value G by addingthe first and second sums together; (l) a complex number generator incommunication with the adder and the ratio function unit for creating acomplex number based on the phase adjustment value θ and the gainadjustment value G; and (m) a multiplier in communication with the inputto the WTRU and the complex number generator for multiplying each of thereceived individual symbols by the created complex number, wherein themultiplier outputs corrected constellation pattern data.
 14. The WTRU ofclaim 13 wherein the predetermined function performed on m is (m−1)/2.15. The WTRU of claim 13 wherein the created complex number has aamplitude equal to the inverse of the gain adjustment value G, and aphase equal to the phase adjustment value θ.
 16. The WTRU of claim 13wherein the WTRU operates in conjunction with a frequency divisionmultiplexing (FDM) system, and the constellation pattern data iscorrected as a function of time and frequency.
 17. The WTRU of claim 13further comprising: (n) a logical router in communication with the firstand second absolute value units, the first and second summers, and thequadrant union detector, wherein the logical router is configured toroute absolute values of the real symbol components to the first summerbased on whether the quadrant union detector identifies the real symbolcomponents as being associated with the first quadrant union or thesecond quadrant union.
 18. The WTRU of claim 13 further comprising: (n)a logical router in communication with the first and second absolutevalue units, the first and second summers, and the quadrant uniondetector, wherein the logical router is configured to route absolutevalues of the imaginary symbol components to the first summer based onwhether the quadrant union detector identifies the imaginary symbolcomponents as being associated with the first quadrant union or thesecond quadrant union.
 19. The WTRU of claim 13 further comprising: (n)a logical router in communication with the first and second absolutevalue units, the first and second summers, and the quadrant uniondetector, wherein the logical router is configured to route absolutevalues of the real symbol components to the second summer based onwhether the quadrant union detector identifies the real symbolcomponents as being associated with the first quadrant union or thesecond quadrant union.
 20. The WTRU of claim 13 further comprising: (n)a logical router in communication with the first and second absolutevalue units, the first and second summers, and the quadrant uniondetector, wherein the logical router is configured to route absolutevalues of the imaginary symbol components to the second summer based onwhether the quadrant union detector identifies the imaginary symbolcomponents as being associated with the first quadrant union or thesecond quadrant union.
 21. An integrated circuit (IC) for correcting thephase and gain of data associated with a constellation pattern of aplurality of individual symbols received by an input to the IC, theconstellation pattern having a first quadrant union including a firstquadrant and a third quadrant, and a second quadrant union including asecond quadrant and a fourth quadrant, the IC comprising: (a) a symbolcomponent divider for dividing each individual symbol into real andimaginary symbol components, the symbol divider being configured tooutput the real symbol components via a first output and the imaginarysymbol components via a second output; (b) a real component signdetector in communication with the first output of the symbol componentdivider for receiving the real symbol components and determining thesigns of the real symbol components; (c) an imaginary component signdetector in communication with the second output of the symbol componentdivider for receiving the imaginary symbol components and determiningthe signs of the imaginary symbol components; (d) a quadrant uniondetector in communication with the real component sign detector and theimaginary component sign detector for receiving an indication of thesigns of the real and imaginary symbol components, the quadrant uniondetector being configured to identify whether the individual symbol isassociated with the first quadrant union or the second quadrant unionbased on the received indication; (e) a first absolute value unit incommunication with the first output of the symbol component divider foroutputting the absolute values of the real symbol components; (f) asecond absolute value unit in communication with the second output ofthe symbol component divider for outputting the absolute values of theimaginary symbol components; (g) a first summer for creating a first sumof the absolute values of the real symbol components identified by thequadrant union detector as being associated with the second quadrantunion and the absolute values of the imaginary symbol componentsidentified by the quadrant union detector as being associated with thefirst quadrant union; (h) a second summer for creating a second sum ofthe absolute values of the real symbol components identified by thequadrant union detector as being associated with the first quadrantunion and the absolute values of the imaginary symbol componentsidentified by the quadrant union detector as being associated with thesecond quadrant union; (i) a ratio calculation unit in communicationwith the first and second summers for determining a sum ratio m bydividing the first sum by the second sum; (j) a ratio function unit incommunication with the ratio calculation unit for performing apredetermined function on the sum ratio m to determine a phaseadjustment value θ; (k) an adder in communication with the first andsecond summers for determining a gain adjustment value G by adding thefirst and second sums together; (l) a complex number generator incommunication with the adder and the ratio function unit for creating acomplex number based on the phase adjustment value θ and the gainadjustment value G; and (m) a multiplier in communication with the inputto the IC and the complex number generator for multiplying each of thereceived individual symbols by the created complex number, wherein themultiplier outputs corrected constellation pattern data.
 22. The IC ofclaim 21 wherein the predetermined function performed on m is (m−1)/2.23. The IC of claim 21 wherein the created complex number has aamplitude equal to the inverse of the gain adjustment value G, and aphase equal to the phase adjustment value θ.
 24. The IC of claim 21wherein the IC operates in conjunction with a frequency divisionmultiplexing (FDM) system, and the constellation pattern data iscorrected as a function of time and frequency.
 25. The IC of claim 21further comprising: (n) a logical router in communication with the firstand second absolute value units, the first and second summers, and thequadrant union detector, wherein the logical router is configured toroute absolute values of the real symbol components to the first summerbased on whether the quadrant union detector identifies the real symbolcomponents as being associated with the first quadrant union or thesecond quadrant union.
 26. The IC of claim 21 further comprising: (n) alogical router in communication with the first and second absolute valueunits, the first and second summers, and the quadrant union detector,wherein the logical router is configured to route absolute values of theimaginary symbol components to the first summer based on whether thequadrant union detector identifies the imaginary symbol components asbeing associated with the first quadrant union or the second quadrantunion.
 27. The IC of claim 21 further comprising: (n) a logical routerin communication with the first and second absolute value units, thefirst and second summers, and the quadrant union detector, wherein thelogical router is configured to route absolute values of the real symbolcomponents to the second summer based on whether the quadrant uniondetector identifies the real symbol components as being associated withthe first quadrant union or the second quadrant union.
 28. The IC ofclaim 21 further comprising: (n) a logical router in communication withthe first and second absolute value units, the first and second summers,and the quadrant union detector, wherein the logical router isconfigured to route absolute values of the imaginary symbol componentsto the second summer based on whether the quadrant union detectoridentifies the imaginary symbol components as being associated with thefirst quadrant union or the second quadrant union.